Radio-frequency devices with gate node voltage compensation

ABSTRACT

Radio-frequency (RF) devices are disclosed having transistor gate voltage compensation to provide improved switching performance. RF devices, such as switches, include a plurality of field-effect transistors (FETs) connected in series between first and second nodes, each FET having a gate. A compensation network including a coupling circuit couples the gates of each pair of neighboring FETs.

RELATED APPLICATION

This application is a divisional of U.S. patent application Ser. No. 13/936,177, filed on Jul. 6, 2013, entitled “Radio-Frequency Switch Having Gate Node Voltage Compensation Network,” which claims priority to U.S. Provisional Application No. 61/669,049, filed on Jul. 7, 2012, and entitled “Radio-Frequency Switch Having Gate Node Voltage Compensation Network,” the disclosures of which are hereby incorporated by reference in their entirety.

BACKGROUND

Field

The present disclosure generally relates to the field of electronics, and more particularly, to radio-frequency switches.

Description of Related Art

Radio-frequency (RF) switches, such as transistor switches, can be used to switch signals between one or more poles and one or more throws. Transistor switches, or portions thereof, can be controlled through transistor biasing and/or coupling. Design and use of bias and/or coupling circuits in connection with RF switches can affect switching performance.

SUMMARY

In some implementations, the present disclosure relates to a radio-frequency (RF) switch that includes a plurality of field-effect transistors (FETs) connected in series between first and second nodes, with each FET having a gate. The RF switch further includes a compensation network having a coupling circuit that couples the gates of each pair of neighboring FETs.

In some embodiments, at least some of the FETs can be silicon-on-insulator (SOI) FETs. In some embodiments, the compensation network can be configured to reduce voltage swings across each of the plurality of FETs. In some embodiments, The switch can further include a feed-forward circuit that couples a source of an end FET to the gate of the end FET. The feed-forward circuit can include a capacitor. The feed-forward circuit can further include a resistor in series with the capacitor.

In some embodiments, the coupling circuit can include a capacitor. The capacitors can have successively smaller capacitance values as the FETs are traversed from the first node to the second node. The coupling circuit can further include a resistor in series with the capacitor.

In some embodiments, the coupling circuit can include a resistor. In some embodiments, the switch can further include a gate bias network connected to and configured to provide bias signals to the gates of the FETs. The gate bias network can be configured so that all of the gates receive a common bias signal.

In some embodiments, the switch can further include a body bias network connected to and configured to provide bias signals to the bodies of the FETs. The body bias network can be configured so that all of the bodies receive a common bias signal.

In some embodiments, the first node can be configured to receive an RF signal having a power value and the second node can be configured to output the RF signal when the FET is in an ON state. The at least one FET can include N FETs connected in series, with the quantity N being selected to allow the switch circuit to handle the power of the RF signal.

According to a number of implementations, the present disclosure relates to a method for operating a radio-frequency (RF) switch. The method includes controlling a plurality of field-effect transistors (FETs) connected in series between first and second nodes so that the FETs are collectively in an ON state or an OFF state, with each FET having a gate. The method further includes coupling the gates of each of neighboring FETs to reduce voltage swings across each of the plurality of FETs.

In accordance with a number of implementations, the present disclosure relates to a semiconductor die that includes a semiconductor substrate and a plurality of field-effect transistors (FETs) formed on the semiconductor substrate and connected in series, with each FET having a gate. The die further includes a compensation network formed on the semiconductor substrate, the compensation network including a coupling circuit that couples the gates of each pair of neighboring FETs.

In some embodiments, the die can further include an insulator layer disposed between the FETs and the semiconductor substrate. The die can be a silicon-on-insulator (SOI) die.

In a number of implementations, the present disclosure relates to a method for fabricating a semiconductor die. The method includes providing a semiconductor substrate and forming a plurality of field-effect transistors (FETs) on the semiconductor substrate so as to be connected in series, with each FET having a gate. The method further includes forming a coupling circuit on the semiconductor substrate so as to couple the gates of each pair of neighboring FETs.

In some embodiments, the method can further include forming an insulator layer between the FETs and the semiconductor substrate.

In a number of implementations, the present disclosure relates to a radio-frequency (RF) switch module that includes a packaging substrate configured to receive a plurality of components. The module further includes a semiconductor die mounted on the packaging substrate. The die includes a plurality of field-effect transistors (FETs) connected in series, with each FET having a gate. The module further includes a compensation network having a coupling circuit that couples the gates of each pair of neighboring FETs.

In some embodiments, the semiconductor die can be a silicon-on-insulator (SOI) die. In some embodiments, the compensation network can be part of the same semiconductor die as the at least one FET. In some embodiments, the compensation network can be part of a second die mounted on the packaging substrate. In some embodiments, the compensation network can be disposed

According to some implementations, the present disclosure relates to a wireless device that includes a transceiver configured to process RF signals. The wireless device further includes an antenna in communication with the transceiver configured to facilitate transmission of an amplified RF signal. The wireless device further includes a power amplifier connected to the transceiver and configured to generate the amplified RF signal. The wireless device further includes a switch connected to the antenna and the power amplifier and configured to selectively route the amplified RF signal to the antenna. The switch includes a plurality of field-effect transistors (FETs) connected in series, with each FET having a gate. The switch further includes a compensation network having a coupling circuit that couples the gates of each pair of neighboring FETs.

BRIEF DESCRIPTION OF THE DRAWINGS

Various embodiments are depicted in the accompanying drawings for illustrative purposes, and should in no way be interpreted as limiting the scope of the inventions. In addition, various features of different disclosed embodiments can be combined to form additional embodiments, which are part of this disclosure. Throughout the drawings, reference numbers may be reused to indicate correspondence between reference elements.

FIG. 1 schematically shows a radio-frequency (RF) switch configured to switch one or more signals between one or more poles and one or more throws.

FIG. 2 shows that the RF switch 100 of FIG. 1 can include an RF core and an energy management (EM) core.

FIG. 3 shows an example of the RF core implemented in an single-pole-double-throw (SPDT) configuration.

FIG. 4 shows an example of the RF core implemented in an SPDT configuration where each switch arm can include a plurality of field-effect transistors (FETs) connected in series.

FIG. 5 schematically shows that controlling of one or more FETs in an RF switch can be facilitated by a circuit configured to bias and/or couple one or more portions of the FETs.

FIG. 6 shows examples of the bias/coupling circuit implemented on different parts of a plurality of FETs in a switch arm.

FIGS. 7A and 7B show plan and side sectional views of an example finger-based FET device implemented in a silicon-on-insulator (SOI) configuration.

FIGS. 8A and 8B show plan and side sectional views of an example of a multiple-finger FET device implemented in an SOI configuration.

FIGS. 9-11 show variations of a tenth example of an RF switch circuit having FETs whose gates can be voltage-compensated to, for example, yield an improved voltage distribution across each FET.

FIG. 12 shows an example of performance improvement that can be achieved with the gate-compensation feature of FIGS. 9-11.

FIGS. 13A-13D show examples of how various components for biasing, coupling, and/or facilitating the example configurations of FIGS. 9-10 can be implemented.

FIGS. 14A and 14B show an example of a packaged module that can include one or more features described herein.

FIG. 15 shows that in some embodiments, one or more features of the present disclosure can be implemented in a switch device such as a single-pole-multi-throw (SPMT) switch configured to facilitate multi-band multi-mode wireless operation.

FIG. 16 shows an example of a wireless device that can include one or more features described herein.

DETAILED DESCRIPTION

The headings provided herein, if any, are for convenience only and do not necessarily affect the scope or meaning of the claimed invention.

Example Components of a Switching Device:

FIG. 1 schematically shows a radio-frequency (RF) switch 100 configured to switch one or more signals between one or more poles 102 and one or more throws 104. In some embodiments, such a switch can be based on one or more field-effect transistors (FETs) such as silicon-on-insulator (SOI) FETs. When a particular pole is connected to a particular throw, such a path is commonly referred to as being closed or in an ON state. When a given path between a pole and a throw is not connected, such a path is commonly referred to as being open or in an OFF state.

FIG. 2 shows that in some implementations, the RF switch 100 of FIG. 1 can include an RF core 110 and an energy management (EM) core 112. The RF core 110 can be configured to route RF signals between the first and second ports. In the example single-pole-double-throw (SPDT) configuration shown in FIG. 2, such first and second ports can include a pole 102 a and a first throw 104 a, or the pole 102 a and a second throw 104 b.

In some embodiments, EM core 112 can be configured to supply, for example, voltage control signals to the RF core. The EM core 112 can be further configured to provide the RF switch 100 with logic decoding and/or power supply conditioning capabilities.

In some embodiments, the RF core 110 can include one or more poles and one or more throws to enable passage of RF signals between one or more inputs and one or more outputs of the switch 100. For example, the RF core 110 can include a single-pole double-throw (SPDT or SP2T) configuration as shown in FIG. 2.

In the example SPDT context, FIG. 3 shows a more detailed example configuration of an RF core 110. The RF core 110 is shown to include a single pole 102 a coupled to first and second throw nodes 104 a, 104 b via first and second transistors (e.g., FETs) 120 a, 120 b. The first throw node 104 a is shown to be coupled to an RF ground via an FET 122 a to provide shunting capability for the node 104 a. Similarly, the second throw node 104 b is shown to be coupled to the RF ground via an FET 122 b to provide shunting capability for the node 104 b.

In an example operation, when the RF core 110 is in a state where an RF signal is being passed between the pole 102 a and the first throw 104 a, the FET 120 a between the pole 102 a and the first throw node 104 a can be in an ON state, and the FET 120 b between the pole 102 a and the second throw node 104 b can be in an OFF state. For the shunt FETs 122 a, 122 b, the shunt FET 122 a can be in an OFF state so that the RF signal is not shunted to ground as it travels from the pole 102 a to the first throw node 104 a. The shunt FET 122 b associated with the second throw node 104 b can be in an ON state so that any RF signals or noise arriving at the RF core 110 through the second throw node 104 b is shunted to the ground so as to reduce undesirable interference effects to the pole-to-first-throw operation.

Although the foregoing example is described in the context of a single-pole-double-throw configuration, it will be understood that the RF core can be configured with other numbers of poles and throws. For example, there may be more than one poles, and the number of throws can be less than or greater than the example number of two.

In the example of FIG. 3, the transistors between the pole 102 a and the two throw nodes 104 a, 104 b are depicted as single transistors. In some implementations, such switching functionalities between the pole(s) and the throw(s) can be provided by switch arm segments, where each switch arm segment includes a plurality of transistors such as FETs.

An example RF core configuration 130 of an RF core having such switch arm segments is shown in FIG. 4. In the example, the pole 102 a and the first throw node 104 a are shown to be coupled via a first switch arm segment 140 a. Similarly, the pole 102 a and the second throw node 104 b are shown to be coupled via a second switch arm segment 140 b. The first throw node 104 a is shown to be capable of being shunted to an RF ground via a first shunt arm segment 142 a. Similarly, the second throw node 104 b is shown to be capable of being shunted to the RF ground via a second shunt arm segment 142 b.

In an example operation, when the RF core 130 is in a state where an RF signal is being passed between the pole 102 a and the first throw node 104 a, all of the FETs in the first switch arm segment 140 a can be in an ON state, and all of the FETs in the second switch arm segment 104 b can be in an OFF state. The first shunt arm 142 a for the first throw node 104 a can have all of its FETs in an OFF state so that the RF signal is not shunted to ground as it travels from the pole 102 a to the first throw node 104 a. All of the FETs in the second shunt arm 142 b associated with the second throw node 104 b can be in an ON state so that any RF signals or noise arriving at the RF core 130 through the second throw node 104 b is shunted to the ground so as to reduce undesirable interference effects to the pole-to-first-throw operation.

Again, although described in the context of an SP2T configuration, it will be understood that RF cores having other numbers of poles and throws can also be implemented.

In some implementations, a switch arm segment (e.g., 140 a, 140 b, 142 a, 142 b) can include one or more semiconductor transistors such as FETs. In some embodiments, an FET may be capable of being in a first state or a second state and can include a gate, a drain, a source, and a body (sometimes also referred to as a substrate. In some embodiments, an FET can include a metal-oxide-semiconductor field effect transistor (MOSFET). In some embodiments, one or more FETs can be connected in series forming a first end and a second end such that an RF signal can be routed between the first end and the second end when the FETs are in a first state (e.g., ON state).

At least some of the present disclosure relates to how an FET or a group of FETs can be controlled to provide switching functionalities in desirable manners. FIG. 5 schematically shows that in some implementations, such controlling of an FET 120 can be facilitated by a circuit 150 configured to bias and/or couple one or more portions of the FET 120. In some embodiments, such a circuit 150 can include one or more circuits configured to bias and/or couple a gate of the FET 120, bias and/or couple a body of the FET 120, and/or couple a source/drain of the FET 120.

Schematic examples of how such biasing and/or coupling of different parts of one or more FETs are described in reference to FIG. 6. In FIG. 6, a switch arm segment 140 (that can be, for example, one of the example switch arm segments 140 a, 140 b, 142 a, 142 b of the example of FIG. 4) between nodes 144, 146 is shown to include a plurality of FETs 120. Operations of such FETs can be controlled and/or facilitated by a gate bias/coupling circuit 150 a, and a body bias/coupling circuit 150 c, and/or a source/drain coupling circuit 150 b.

Gate Bias/Coupling Circuit

In the example shown in FIG. 6, the gate of each of the FETs 120 can be connected to the gate bias/coupling circuit 150 a to receive a gate bias signal and/or couple the gate to another part of the FET 120 or the switch arm 140. In some implementations, designs or features of the gate bias/coupling circuit 150 a can improve performance of the switch arm 140. Such improvements in performance can include, but are not limited to, device insertion loss, isolation performance, power handling capability and/or switching device linearity.

Body Bias/Coupling Circuit

As shown in FIG. 6, the body of each FET 120 can be connected to the body bias/coupling circuit 150 c to receive a body bias signal and/or couple the body to another part of the FET 120 or the switch arm 140. In some implementations, designs or features of the body bias/coupling circuit 150 c can improve performance of the switch arm 140. Such improvements in performance can include, but are not limited to, device insertion loss, isolation performance, power handling capability and/or switching device linearity.

Source/Drain Coupling Circuit

As shown in FIG. 6, the source/drain of each FET 120 can be connected to the coupling circuit 150 b to couple the source/drain to another part of the FET 120 or the switch arm 140. In some implementations, designs or features of the coupling circuit 150 b can improve performance of the switch arm 140. Such improvements in performance can include, but are not limited to, device insertion loss, isolation performance, power handling capability and/or switching device linearity.

Examples of Switching Performance Parameters:

Insertion Loss

A switching device performance parameter can include a measure of insertion loss. A switching device insertion loss can be a measure of the attenuation of an RF signal that is routed through the RF switching device. For example, the magnitude of an RF signal at an output port of a switching device can be less than the magnitude of the RF signal at an input port of the switching device. In some embodiments, a switching device can include device components that introduce parasitic capacitance, inductance, resistance, or conductance into the device, contributing to increased switching device insertion loss. In some embodiments, a switching device insertion loss can be measured as a ratio of the power or voltage of an RF signal at an input port to the power or voltage of the RF signal at an output port of the switching device. Decreased switching device insertion loss can be desirable to enable improved RF signal transmission.

Isolation

A switching device performance parameter can also include a measure of isolation. Switching device isolation can be a measure of the RF isolation between an input port and an output port an RF switching device. In some embodiments, it can be a measure of the RF isolation of a switching device while the switching device is in a state where an input port and an output port are electrically isolated, for example while the switching device is in an OFF state. Increased switching device isolation can improve RF signal integrity. In certain embodiments, an increase in isolation can improve wireless communication device performance.

Intermodulation Distortion

A switching device performance parameter can further include a measure of intermodulation distortion (IMD) performance. Intermodulation distortion (IMD) can be a measure of non-linearity in an RF switching device.

IMD can result from two or more signals mixing together and yielding frequencies that are not harmonic frequencies. For example, suppose that two signals have fundamental frequencies f₁ and f₂ (f₂>f₁) that are relatively close to each other in frequency space. Mixing of such signals can result in peaks in frequency spectrum at frequencies corresponding to different products of fundamental and harmonic frequencies of the two signals. For example, a second-order intermodulation distortion (also referred to as IMD2) is typically considered to include frequencies f₁+f₂ f₂−f₁, 2f₁, and 2f₂. A third-order IMD (also referred to as IMD3) is typically considered to include 2f₁+f₂, 2f₁−f₂, f₁+2f₂, f₁−2f₂. Higher order products can be formed in similar manners.

In general, as the IMD order number increases, power levels decrease. Accordingly, second and third orders can be undesirable effects that are of particular interest. Higher orders such as fourth and fifth orders can also be of interest in some situations.

In some RF applications, it can be desirable to reduce susceptibility to interference within an RF system. Non linearity in RF systems can result in introduction of spurious signals into the system. Spurious signals in the RF system can result in interference within the system and degrade the information transmitted by RF signals. An RF system having increased non-linearity can demonstrate increased susceptibility to interference. Non-linearity in system components, for example switching devices, can contribute to the introduction of spurious signals into the RF system, thereby contributing to degradation of overall RF system linearity and IMD performance.

In some embodiments, RF switching devices can be implemented as part of an RF system including a wireless communication system. IMD performance of the system can be improved by increasing linearity of system components, such as linearity of an RF switching device. In some embodiments, a wireless communication system can operate in a multi-band and/or multi-mode environment. Improvement in intermodulation distortion (IMD) performance can be desirable in wireless communication systems operating in a multi-band and/or multi-mode environment. In some embodiments, improvement of a switching device IMD performance can improve the IMD performance of a wireless communication system operating in a multi-mode and/or multi-band environment.

Improved switching device IMD performance can be desirable for wireless communication devices operating in various wireless communication standards, for example for wireless communication devices operating in the LTE communication standard. In some RF applications, it can be desirable to improve linearity of switching devices operating in wireless communication devices that enable simultaneous transmission of data and voice communication. For example, improved IMD performance in switching devices can be desirable for wireless communication devices operating in the LTE communication standard and performing simultaneous transmission of voice and data communication (e.g., SVLTE).

High Power Handling Capability

In some RF applications, it can be desirable for RF switching devices to operate under high power while reducing degradation of other device performance parameters. In some embodiments, it can be desirable for RF switching devices to operate under high power with improved intermodulation distortion, insertion loss, and/or isolation performance.

In some embodiments, an increased number of transistors can be implemented in a switch arm segment of a switching device to enable improved power handling capability of the switching device. For example, a switch arm segment can include an increased number of FETs connected in series, an increased FET stack height, to enable improved device performance under high power. However, in some embodiments, increased FET stack height can degrade the switching device insertion loss performance.

Examples of FET Structures and Fabrication Process Technologies:

A switching device can be implemented on-die, off-die, or some combination thereon. A switching device can also be fabricated using various technologies. In some embodiments, RF switching devices can be fabricated with silicon or silicon-on-insulator (SOI) technology.

As described herein, an RF switching device can be implemented using silicon-on-insulator (SOI) technology. In some embodiments, SOI technology can include a semiconductor substrate having an embedded layer of electrically insulating material, such as a buried oxide layer beneath a silicon device layer. For example, an SOI substrate can include an oxide layer embedded below a silicon layer. Other insulating materials known in the art can also be used.

Implementation of RF applications, such as an RF switching device, using SOI technology can improve switching device performance. In some embodiments, SOI technology can enable reduced power consumption. Reduced power consumption can be desirable in RF applications, including those associated with wireless communication devices. SOI technology can enable reduced power consumption of device circuitry due to decreased parasitic capacitance of transistors and interconnect metallization to a silicon substrate. Presence of a buried oxide layer can also reduce junction capacitance or use of high resistivity substrate, enabling reduced substrate related RF losses. Electrically isolated SOI transistors can facilitate stacking, contributing to decreased chip size.

In some SOI FET configurations, each transistor can be configured as a finger-based device where the source and drain are rectangular shaped (in a plan view) and a gate structure extends between the source and drain like a rectangular shaped finger. FIGS. 7A and 7B show plan and side sectional views of an example finger-based FET device implemented on SOI. As shown, FET devices described herein can include a p-type FET or an n-type FET. Thus, although some FET devices are described herein as p-type devices, it will be understood that various concepts associated with such p-type devices can also apply to n-type devices.

As shown in FIGS. 7A and 7B, a pMOSFET can include an insulator layer formed on a semiconductor substrate. The insulator layer can be formed from materials such as silicon dioxide or sapphire. An n-well is shown to be formed in the insulator such that the exposed surface generally defines a rectangular region. Source (S) and drain (D) are shown to be p-doped regions whose exposed surfaces generally define rectangles. As shown, S/D regions can be configured so that source and drain functionalities are reversed.

FIGS. 7A and 7B further show that a gate (G) can be formed on the n-well so as to be positioned between the source and the drain. The example gate is depicted as having a rectangular shape that extends along with the source and the drain. Also shown is an n-type body contact. Formations of the rectangular shaped well, source and drain regions, and the body contact can be achieved by a number of known techniques. In some embodiments, the source and drain regions can be formed adjacent to the ends of their respective upper insulator layers, and the junctions between the body and the source/drain regions on the opposing sides of the body can extend substantially all the way down to the top of the buried insulator layer. Such a configuration can provide, for example, reduced source/drain junction capacitance. To form a body contact for such a configuration, an additional gate region can be provided on the side so as to allow, for example, an isolated P+ region to contact the Pwell.

FIGS. 8A and 8B show plan and side sectional views of an example of a multiple-finger FET device implemented on SOI. Formations of rectangular shaped n-well, rectangular shaped p-doped regions, rectangular shaped gates, and n-type body contact can be achieved in manners similar to those described in reference to FIGS. 7A and 7B.

The example multiple-finger FET device of FIGS. 8A and 8B can be made to operate such that a drain of one FET acts as a source of its neighboring FET. Thus, the multiple-finger FET device as a whole can provide a voltage-dividing functionality. For example, an RF signal can be provided at one of the outermost p-doped regions (e.g., the leftmost p-doped region); and as the signal passes through the series of FETs, the signal's voltage can be divided among the FETs. In such an example, the rightmost p-doped region can act as an overall drain of the multi-finger FET device.

In some implementations, a plurality of the foregoing multi-finger FET devices can be connected in series as a switch to, for example, further facilitate the voltage-dividing functionality. A number of such multi-finger FET devices can be selected based on, for example, power handling requirement of the switch.

Examples of Bias and/or Coupling Configurations for Improved Performance:

Described herein are various examples of how FET-based switch circuits can be biased and/or coupled to yield one or more performance improvements. In some embodiments, such biasing/coupling configurations can be implemented in SOI FET-based switch circuits. It will be understood that some of the example biasing/coupling configurations can be combined to yield a combination of desirable features that may not be available to the individual configurations. It will also be understood that, although described in the context of RF switching applications, one or more features described herein can also be applied to other circuits and devices that utilize FETs such as SOI FETs.

Example Configurations

In many radio-frequency (RF) transmit applications, switch designs typically require high-power operation capability, especially under mismatch. For example, switches used for antenna tuning are expected to withstand mismatch as high as 20:1 under +35 dBm input power. Also, some switches utilized in wireless systems such as GSM are expected to withstand 5:1 mismatch under +35 dBm input power. Higher field-effect transistor (FET) stack height is generally used to withstand high power under mismatch. However, uneven voltage distribution across the FET stack can lead to harmonic peaking, degradation in compression point, and/or intermodulation distortion (IMD) of SOI-based switches.

FIG. 9 shows an example configuration of an FET stack 520 configured to provide switching of RF signals between first and second nodes 144, 146. The first and second nodes 144, 146 can be, for example, RF input and RF output, respectively.

In some implementations, the stack 520 can include N SOI FETs (indicated as M1, M2, . . . , MN) connected in series between the nodes 144, 146. The number N can be selected based on power handling requirement. For example, N can be increased to handle higher power.

In the example stack configuration 520, each gate of the FET is shown to be biased through a gate resistor Rg. N such gate resistors corresponding to the N FETs are shown to be connected to a common gate bias voltage source “G.”

In the example stack configuration 520, each body of the FET is shown to be biased through a body resistor Rb. N such body resistors corresponding to the N FETs are shown to be connected to a common body bias voltage source “B.”

In some implementations, some or all of the gates of the FETs can be voltage-compensated to yield an improved voltage distribution across each FET in the stack 520. Such an improved voltage distribution can result in improvement in compression point, harmonics, and or IMD performance.

In the example shown in FIG. 9, the foregoing voltage-compensation of the gates can be achieved by coupling the gates of the FETs with capacitive elements Cgg (e.g., capacitors). For example, Cgg1 couples the gates of M1 and M2, Cgg2 couples the gates of M2 and M3, and so on, with Cgg(N−2) coupling the gates of M(N−2) and M(N−1), and Cgg(N−1) coupling the gates of M(N−1) and MN.

In some embodiments, the coupling capacitive elements Cgg can have substantially the same value. In some embodiments, the capacitive elements Cgg can be scaled and/or optimized within the stack 520 with different values for Cgg1, Cgg2, Cgg3, etc. An example of such scaling of Cgg values to obtain a desired result is described in greater detail in reference to FIG. 12.

In some embodiments, a feed-forward capacitor, Cfwd can be provided to couple source/drain and gate of an end FET (e.g., M1). In some embodiments, the feed-forward capacitor Cfwd can couple source/drain and gate of a non-end FET within the FET stack. The feed-forward capacitor, Cfwd can ensure that the RF signal path between the nodes 144, 146 is coupled to at least one of the gates of the FETs.

FIG. 10 shows that in some implementations, voltage-compensation of the gates can be achieved by coupling the gates of the FETs with resistive elements Rgg (e.g., resistors). For example, Rgg1 couples the gates of M1 and M2, Rgg2 couples the gates of M2 and M3, and so on, with Rgg(N−2) coupling the gates of M(N−2) and M(N−1), and Rgg(N−1) coupling the gates of M(N−1) and MN. In the example of FIG. 10, a feed-forward coupling between source/drain and gate of an FET (e.g., M1) is shown to include a capacitor Cfwd in series with a resistor Rfwd.

In some embodiments, the coupling resistive elements Rgg can have substantially the same value. In some embodiments, the resistive elements Rgg can have different values that are selected to achieve a desired result.

FIG. 11 shows that in some implementations, voltage-compensation of the gates can be achieved by coupling the gates of the FETs with capacitive elements Cgg (e.g., capacitors) and resistive elements Rgg (e.g., resistors). For example, Cgg1 and Rgg1 in series couples the gates of M1 and M2, Cgg2 and Rgg2 in series couples the gates of M2 and M3, and so on, with Cgg(N−2) and Rgg(N−2) in series coupling the gates of M(N−2) and M(N−1), and Cgg(N−1) and Rgg(N−1) in series coupling the gates of M(N−1) and MN. In the example of FIG. 11, a feed-forward coupling between source/drain and gate of an FET (e.g., M1) is shown to include a capacitor Cfwd in series with a resistor Rfwd.

In some embodiments, the coupling capacitive elements Cgg can have substantially the same value. In some embodiments, the capacitive elements Cgg can have different values that are selected to achieve a desired result. Similarly, the coupling resistive elements Rgg can have substantially the same value, or have different values selected to achieve a desired result.

FIG. 12 shows plots of voltage swings across each of the FETs in an example stack having 16 FETs. The “baseline” configuration corresponds to a stack where the gates are not voltage-compensated. The “gate compensation” configuration corresponds to a stack where the gates are voltage-compensated as described in reference to FIG. 9. For the plot shown in FIG. 12, the values of Cgg are selected as Cgg1>Cgg2>Cgg3> . . . >CggN. Voltage swings associated with such a configuration are shown to be significantly less than the baseline case.

In some embodiments, the capacitive elements Cgg described in reference to FIGS. 9 and 11 can be implemented on the same die as the FETs (M1, M2, etc.), off of the die, or any combination thereof. Such on-die and/or off-die implementations of the capacitive elements Cgg can include, for example, MIM capacitors and/or capacitive metal traces.

In some embodiments, the resistive elements Rgg described in reference to FIGS. 10 and 11 can be implemented on the same die as the FETs (M1, M2, etc.), off of the die, or any combination thereof.

In some implementations, and as described herein, the foregoing example configurations described in reference to FIGS. 9-12 can be relatively simpler and easier to implement, and can yield a number of improvements. For example, this technique can provide less fluctuations in voltage swings across each FET in a switch stack. Such a feature can yield other desirable features such as improved compression point, as well as improved harmonics and IMD performance.

In some implementations, various example configurations related to gate-to-gate compensation can be combined with one or more features that can improve performance of one or more of the FETs in a given stack.

Examples of Implementations in Products:

Various examples of FET-based switch circuits and bias/coupling configurations described herein can be implemented in a number of different ways and at different product levels. Some of such product implementations are described by way of examples.

Semiconductor Die Implementation

FIGS. 13A-13D schematically show non-limiting examples of such implementations on one or more semiconductor die. FIG. 13A shows that in some embodiments, a switch circuit 120 and a bias/coupling circuit 150 having one or more features as described herein can be implemented on a die 800. FIG. 13B shows that in some embodiments, at least some of the bias/coupling circuit 150 can be implemented outside of the die 800 of FIG. 13A.

FIG. 13C shows that in some embodiments, a switch circuit 120 having one or more features as described herein can be implemented on a first die 800 a, and a bias/coupling circuit 150 having one or more features as described herein can be implemented on a second die 800 b. FIG. 13D shows that in some embodiments, at least some of the bias/coupling circuit 150 can be implemented outside of the first die 800 a of FIG. 13C.

Packaged Module Implementation

In some embodiments, one or more die having one or more features described herein can be implemented in a packaged module. An example of such a module is shown in FIGS. 14A (plan view) and 14B (side view). Although described in the context of both of the switch circuit and the bias/coupling circuit being on the same die (e.g., example configuration of FIG. 13A), it will be understood that packaged modules can be based on other configurations.

A module 810 is shown to include a packaging substrate 812. Such a packaging substrate can be configured to receive a plurality of components, and can include, for example, a laminate substrate. The components mounted on the packaging substrate 812 can include one or more dies. In the example shown, a die 800 having a switching circuit 120 and a bias/coupling circuit 150 is shown to be mounted on the packaging substrate 812. The die 800 can be electrically connected to other parts of the module (and with each other where more than one die is utilized) through connections such as connection-wirebonds 816. Such connection-wirebonds can be formed between contact pads 818 formed on the die 800 and contact pads 814 formed on the packaging substrate 812. In some embodiments, one or more surface mounted devices (SMDs) 822 can be mounted on the packaging substrate 812 to facilitate various functionalities of the module 810.

In some embodiments, the packaging substrate 812 can include electrical connection paths for interconnecting the various components with each other and/or with contact pads for external connections. For example, a connection path 832 is depicted as interconnecting the example SMD 822 and the die 800. In another example, a connection path 832 is depicted as interconnecting the SMD 822 with an external-connection contact pad 834. In yet another example a connection path 832 is depicted as interconnecting the die 800 with ground-connection contact pads 836.

In some embodiments, a space above the packaging substrate 812 and the various components mounted thereon can be filled with an overmold structure 830. Such an overmold structure can provide a number of desirable functionalities, including protection for the components and wirebonds from external elements, and easier handling of the packaged module 810.

FIG. 15 shows a schematic diagram of an example switching configuration that can be implemented in the module 810 described in reference to FIGS. 14A and 14B. In the example, the switch circuit 120 is depicted as being an SP9T switch, with the pole being connectable to an antenna and the throws being connectable to various Rx and Tx paths. Such a configuration can facilitate, for example, multi-mode multi-band operations in wireless devices.

The module 810 can further include an interface for receiving power (e.g., supply voltage VDD) and control signals to facilitate operation of the switch circuit 120 and/or the bias/coupling circuit 150. In some implementations, supply voltage and control signals can be applied to the switch circuit 120 via the bias/coupling circuit 150.

Wireless Device Implementation

In some implementations, a device and/or a circuit having one or more features described herein can be included in an RF device such as a wireless device. Such a device and/or a circuit can be implemented directly in the wireless device, in a modular form as described herein, or in some combination thereof. In some embodiments, such a wireless device can include, for example, a cellular phone, a smart-phone, a hand-held wireless device with or without phone functionality, a wireless tablet, etc.

FIG. 16 schematically depicts an example wireless device 900 having one or more advantageous features described herein. In the context of various switches and various biasing/coupling configurations as described herein, a switch 120 and a bias/coupling circuit 150 can be part of a module 810. In some embodiments, such a switch module can facilitate, for example, multi-band multip-mode operation of the wireless device 900.

In the example wireless device 900, a power amplifier (PA) module 916 having a plurality of PAs can provide an amplified RF signal to the switch 120 (via a duplexer 920), and the switch 120 can route the amplified RF signal to an antenna. The PA module 916 can receive an unamplified RF signal from a transceiver 914 that can be configured and operated in known manners. The transceiver can also be configured to process received signals. The transceiver 914 is shown to interact with a baseband sub-system 910 that is configured to provide conversion between data and/or voice signals suitable for a user and RF signals suitable for the transceiver 914. The transceiver 914 is also shown to be connected to a power management component 906 that is configured to manage power for the operation of the wireless device 900. Such a power management component can also control operations of the baseband sub-system 910 and the module 810.

The baseband sub-system 910 is shown to be connected to a user interface 902 to facilitate various input and output of voice and/or data provided to and received from the user. The baseband sub-system 910 can also be connected to a memory 904 that is configured to store data and/or instructions to facilitate the operation of the wireless device, and/or to provide storage of information for the user.

In some embodiments, the duplexer 920 can allow transmit and receive operations to be performed simultaneously using a common antenna (e.g., 924). In FIG. 16, received signals are shown to be routed to “Rx” paths (not shown) that can include, for example, a low-noise amplifier (LNA).

A number of other wireless device configurations can utilize one or more features described herein. For example, a wireless device does not need to be a multi-band device. In another example, a wireless device can include additional antennas such as diversity antenna, and additional connectivity features such as Wi-Fi, Bluetooth, and GPS.

General Comments:

Unless the context clearly requires otherwise, throughout the description and the claims, the words “comprise,” “comprising,” and the like are to be construed in an inclusive sense, as opposed to an exclusive or exhaustive sense; that is to say, in the sense of “including, but not limited to.” The word “coupled”, as generally used herein, refers to two or more elements that may be either directly connected, or connected by way of one or more intermediate elements. Additionally, the words “herein,” “above,” “below,” and words of similar import, when used in this application, shall refer to this application as a whole and not to any particular portions of this application. Where the context permits, words in the above Detailed Description using the singular or plural number may also include the plural or singular number respectively. The word “or” in reference to a list of two or more items, that word covers all of the following interpretations of the word: any of the items in the list, all of the items in the list, and any combination of the items in the list.

The above detailed description of embodiments of the invention is not intended to be exhaustive or to limit the invention to the precise form disclosed above. While specific embodiments of, and examples for, the invention are described above for illustrative purposes, various equivalent modifications are possible within the scope of the invention, as those skilled in the relevant art will recognize. For example, while processes or blocks are presented in a given order, alternative embodiments may perform routines having steps, or employ systems having blocks, in a different order, and some processes or blocks may be deleted, moved, added, subdivided, combined, and/or modified. Each of these processes or blocks may be implemented in a variety of different ways. Also, while processes or blocks are at times shown as being performed in series, these processes or blocks may instead be performed in parallel, or may be performed at different times.

The teachings of the invention provided herein can be applied to other systems, not necessarily the system described above. The elements and acts of the various embodiments described above can be combined to provide further embodiments.

While certain embodiments of the inventions have been described, these embodiments have been presented by way of example only, and are not intended to limit the scope of the disclosure. Indeed, the novel methods and systems described herein may be embodied in a variety of other forms; furthermore, various omissions, substitutions and changes in the form of the methods and systems described herein may be made without departing from the spirit of the disclosure. The accompanying claims and their equivalents are intended to cover such forms or modifications as would fall within the scope and spirit of the disclosure. 

What is claimed is:
 1. A semiconductor die comprising: a semiconductor substrate; a first field-effect transistor formed on the semiconductor substrate and including a first gate node; a second field-effect transistor connected in series with the first field-effect transistor and including a second gate node; a third field-effect transistor connected in series with the second field-effect transistor and including a third gate node; a first capacitor that is directly connected at a first end to the first gate node, directly connected at a second end to the second gate node, and configured to block DC current flow between the first gate node and the second gate node; and a second capacitor that is directly connected at a first end to the second gate node, directly connected at a second end to the third gate node, and configured to block DC current flow between the second gate node and the third gate node.
 2. The semiconductor die of claim 1 wherein the first and second field-effect transistors are silicon-on-insulator field-effect transistors.
 3. The semiconductor die of claim 1 wherein the first capacitor, second capacitor and a resistor are part of a compensation network configured to reduce voltage swings across each of the first and second field-effect transistors.
 4. The semiconductor die of claim 1 further comprising a feed-forward circuit that couples a source of the first field-effect transistor to the first gate node.
 5. The semiconductor die of claim 4 wherein the feed-forward circuit includes a third capacitor.
 6. The semiconductor die of claim 5 wherein the feed-forward circuit further includes a resistor connected in series with the third capacitor.
 7. The semiconductor die of claim 1 wherein the first capacitor has a higher capacitance value than the second capacitor.
 8. The semiconductor die of claim 1 wherein the first, second and third gate nodes are coupled to a gate bias voltage node.
 9. The semiconductor die of claim 1 further comprising a body bias network connected to, and configured to provide body bias signals to, body nodes of the first, second and third field-effect transistors.
 10. The semiconductor die of claim 9 wherein the body bias network is configured so that each of the first, second and third field-effect transistors receives a common body bias signal.
 11. A method for operating a radio-frequency device, the method comprising: controlling first, second and third field-effect transistors connected in series between first and second nodes so that the first, second and third field-effect transistors are collectively in an ON state or an OFF state; blocking DC current flow between a first gate node of the first field-effect transistor and a second gate node of the second field-effect transistor using a first capacitor that is directly connected at a first end to the first gate node and directly connected at a second end to the second gate node; and blocking DC current flow between the second gate node and a third gate node of the third field-effect transistor using a second capacitor that is directly connected at a first end to the second gate node and directly connected at a second end to the third gate node.
 12. The method of claim 11 further comprising receiving a radio-frequency signal having a power value at the first node and outputting the radio-frequency signal at the second node when the first field-effect transistor is in the ON state.
 13. A wireless device comprising: a transceiver configured to process radio-frequency signals; an antenna in communication with the transceiver configured to facilitate transmission of an amplified radio-frequency signal; a power amplifier connected to the transceiver and configured to generate the amplified radio-frequency signal; and a switch connected to the antenna and the power amplifier and configured to selectively route the amplified radio-frequency signal to the antenna, the switch including a first field-effect transistor including a first gate node, a second field-effect transistor connected in series with the first field-effect transistor and including a second gate node, and a third field-effect transistor connected in series with the second field-effect transistor and including a third gate node, the switch further including a first capacitor that is directly connected at a first end to the first gate node, directly connected at a second end to the second gate node, and configured to block DC current flow between the first gate node and the second gate node, the switch further including a second capacitor that is directly connected at a first end to the second gate node and directly connected at a second end to the third gate node.
 14. The wireless device of claim 13 wherein the switch is formed on a silicon-on-insulator die of the wireless device.
 15. The wireless device of claim 13 wherein the switch is part of a receive path, the switch being connected to an output node for a radio-frequency signal received from the antenna. 